Frequency synthesizer

ABSTRACT

The frequency synthesizer has two fixed frequency dividers, two charge pumps, five capacitors, a voltage controlled oscillator, and a transconductance voltage amplifier. The pulse widths of the input reference signal and the output signal are compared and the resultant signal is coupled to the oscillator to adjust its frequency. The circuit exhibits accurate frequency synthesizing, and thus can be used in wireless communication and signal processing systems. It provides a precise integer and fractional frequency division with a low phase noise. Moreover, it has a simple and compact structure that can be implemented in integrated circuit technologies such as CMOS.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to electronic circuits for generating signals at a desired frequency, and more particularly, to a frequency synthesizer in which the output frequency is adjusted based on comparison of the pulse width of an output signal to a reference signal, and which is capable of generating fractions and multiples of the reference frequency with a fast settling time.

2. Description of the Related Art

A frequency synthesizer is an electronics system or circuit that is used in communication and signal processing systems to generate a range of frequencies from a single stable frequency oscillator. A common approach to realize the frequency synthesizer is based on the Phase Locked Loop (PLL). The PLL is a feedback system which compares the frequencies of its input and output signals; the first component of the PLL system is the frequency or phase detector which carries out the frequency comparison. It is generally understood that error signals, which represents the difference between the input signals, is averaged using a low pass filter (LP) to generate a control signal. The resultant signal is coupled to a VCO to adjust its output frequency. The feedback process is continued to force the error signal to diminish. A frequency divider is inserted in the feedback loop to allow the output frequency to be a multiple of the reference frequency.

One of the desired criteria in the frequency synthesizer system is the fast settling time, which measures the ability of the communication system to perform channels scanning within the allowed acquisition period. Knowing that the loop bandwidth of the frequency synthesizer is inversely related to the settling time, it is therefore recommended to design the system to have a wide loop bandwidth. On the other hand, to minimize spurious emissions generated at the output of the phase detector, it is recommended to select the loop bandwidth to be a tenth of the reference frequency signals F_(ref). Another disadvantage of the limited loop bandwidth is that it results in high close-in phase noise at the output.

Due to its role in the frequency selection of a frequency synthesizer, a frequency divider has received major attention from researchers in the field. Main types of frequency divider include integer frequency divider and fractional frequency divider.

In the former case, the input frequency and output frequency relation is given by F_(out)=MF_(ref). M has integer values that are used to control the output frequency. In communication systems, M controls transmitting and receiving frequency channels. Therefore, F_(ref) is constrained to be equal to the channel spacing to allow for channel selection through M, which imposes a limitation on the loop bandwidth of the PLL. Thus a long settling time is one of the main drawbacks of the PLL based integer frequency divider.

Although different frequency divider structures can be used to realize the M divider, typically, a Pulse Swallow divider is widely used. By simple analysis, it can be shown that M and F_(out) are given by: M=PN+S f _(out) =PNf _(ref) +Sf _(ref).

In contrast to the integer frequency divider, a fractional frequency divider allows the output frequency to be a fraction of the reference frequency. Hence, the reference frequency F_(ref), and consequently the loop bandwidth, can be made much greater than the channel spacing. Thus, the frequency synthesizer-based fractional divider does not suffer from the long settling time. The fractional division ratio is obtained by dividing the output signal by an integer number N for certain number of the output pulses P and by N+1 for another number of S pulses. The effective frequency division ratio M can be given by:

$M = {\frac{{NP} + {\left( {N + 1} \right)S}}{P + S}.}$

A typical frequency synthesizer circuit comprises a fractional frequency divider. However, a frequency synthesizer-based fractional frequency divider suffers from a series effect called fractional spurs, which are generated from dividing the signal frequency by two different values. Fractional spurs modulate the VCO, and hence strong sideband signals are generated around the output frequency.

Thus, a frequency synthesizer solving the aforementioned problems is desired.

SUMMARY OF THE INVENTION

The frequency synthesizer has an input reference signal that is applied to a charge pump circuit in operable communication with a frequency divide-by-two unit, switches, and capacitors, which are arranged to measure the pulse width of the reference signal. A similar circuit configuration measures the pulse width of the output frequency. Pulse widths of both signals (reference and output signals) are subtracted, and the resultant voltage is coupled to the input of a voltage control oscillator (VCO) to adjust its output frequency.

The output of the VCO is fed back to the charge pump unit to complete a negative feedback loop. The frequency synthesizer presents a frequency synthesizing method that is based on the difference between two signals' pulse widths instead of their phase differences, as is done in PLL-based synthesizers. Thus, the method provides accurate frequency synthesis that can be used in wireless communication and signal processing systems. Moreover, the frequency synthesizer circuitry features a precise integer and fractional frequency divider having low phase noise. Additionally, the frequency synthesizer circuit exhibits a simple and compact structure that can be implemented as an integrated circuit.

These and other features of the present invention will become readily apparent upon further review of the following specification and drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of the frequency synthesizer, according to the present invention.

FIG. 2 is a multi-channel plot showing the voltage waveforms at different nodes along f_(ref) path, according to the present invention.

Similar reference characters denote corresponding features consistently throughout the attached drawings.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

As shown in FIG. 1, the frequency synthesizer 5 has a first fixed divide-by-2 frequency divider 10, which accepts a reference frequency f_(ref) as input, and a second fixed divide-by-2 frequency divider 30, which accepts an initial frequency f_(o) as input. The first divider 10 has 0.5f_(ref) and its complement as outputs, which are routed to switches S₂, S₄ S₆, S₇ S₉ and S₁₀ at output of charge pump 20. Charge pump 20 input terminals accept reference frequency f_(ref) and its complement. The f_(ref) signal is routed to switches S₁, S₃, S₅, and S₈ at switched output of charge pump 20. Capacitor C₁ holds charge for the charge pump output at S₉ and S₁₀, respectively which is routed to the negative input of a transconductance amplifier 50 having a predetermined transconductance g_(m).

Charge pump 40 has input terminals that accept initial frequency f_(o) signal and its complement as input. The second divider 30 has 0.5fo and its complement as outputs, which are routed to switches S₁₂, S₁₄ S₁₅, S₁₇ S₁₉ and S₂₀ at charge pump 40. The f_(o) signal and its complement are routed to switches S₁₁, S₁₃, S₁₆, and S₁₈ at switched output of charge pump 40. Capacitors C₃ and C₄ hold charge for the charge pump output at S₁₉ and S₂₀, respectively which is routed to the positive input of transconductance amplifier 50. Output V_(z) of transconductance amplifier 50 is smoothed by capacitor C₅ and controls the frequency of voltage-controlled oscillator 60.

The inventive frequency synthesis circuitry 5 provides the frequency synthesis by comparing the pulse width of both reference signal f_(ref) and output signal f_(o). The pulse widths of the reference frequency f_(ref) and the output frequency f_(o) are sensed and stored at V_(x) and V_(y) nodes respectively. Therefore V_(x) and V_(y) are proportional to the period of f_(ref) and f_(o) signals respectively.

As shown in FIG. 2 the multi-channel plot 200 displays the different states of reference signal f_(ref), and the process of obtaining V_(x). For example, in the case when 0.5f_(ref) signal is high and f_(ref) is low switches S₅₋₆ are ON and the stored voltage across C₁ is discharged to zero volts. When f_(ref) goes high C₁ will be charged for half cycle of f_(ref) by a constant current I₁ provided by the charge pump 20.

By analogy, the voltage across C₂ can be obtained at the different state of signal f_(ref). Capacitor C₁ is connected to V_(x) in a first branch, or alternatively, C₂ is connected to V_(x) in a second branch, thus V_(x) will be updated every cycle of f_(ref). Similarly voltage V_(y), which senses the period of f_(o), can be obtained. The voltage node V_(y) is connected to C₃ in a first branch and C₄ in a second branch, alternatively, to maintain its value updated every cycle of f_(o). V_(x) and V_(y) can be given by:

$\begin{matrix} {{V_{x} = \frac{I_{1}T_{ref}}{2C_{1}}};{C_{1} = C_{2}}} & (1) \\ {{V_{y} = \frac{I_{2}T_{0}}{2C_{3}}};{C_{3} = C_{4}}} & (2) \end{matrix}$ showing that they have proportional relationship with the period of the reference signal T_(ref) and the output signal T_(o), respectively.

V_(y) and V_(x) are applied to the positive and negative terminals of the transconductance amplifier 5 respectively. The resultant output voltage V_(z) of summation unit 50 can be given by:

$\begin{matrix} {V_{z} = {g_{m}{C_{5}\left( {\frac{I_{2}T_{0}}{2C_{3}} - \frac{I_{1}T_{ref}}{2C_{1}}} \right)}}} & (3) \end{matrix}$ The voltage has a proportional relationship with the difference between the periods of f_(ref) and f_(o). The parameter g_(m) represents the transconductance of the amplifier 50.

V_(z) is coupled to the input of the voltage control oscillator VCO 60 to adjust its output frequency to be precisely multiple of f_(ref) according to the following equation,

$\begin{matrix} {{f_{o} = {Kf}_{ref}};{{{where}\mspace{14mu} K} = \frac{I_{2}C_{1}}{I_{1}C_{3}}}} & (4) \end{matrix}$

K represents the multiple factor, which can be realized through ratios of the capacitors and/or the charging currents in the two paths. This factor can be integer or fractional number, which provides a wide programmability feature for the presented invention. Fractional divider allows for easy programmability of K to obtain a desired output frequency and a precise channel selection. In CMOS technology, it is visible to achieve capacitor ratios with an error less than 0.5%, and consequently to implement precise frequency synthesizers.

It is to be understood that the present invention is not limited to the embodiment described above, but encompasses any and all embodiments within the scope of the following claims. 

1. A frequency synthesizer, comprising: a reference fixed frequency divide-by-d divider having an input accepting a reference frequency signal, f_(ref), outputs of the first fixed frequency divider being signals (1/d)f_(ref) and (1/d)f_(ref) , respectively; an output fixed frequency divide-by-d divider having an input that accepts an initial frequency signal, f_(o), outputs of the output fixed frequency divider being signals (1/d)f_(o) and (1/d) f_(o) , respectively; a first controlled switch bank having an input and a capacitively coupled output, wherein the capacitively coupled output of the first controlled switch bank comprises a first capacitor C₁ connected to a first branch of the first controlled switch bank and a second capacitor C₂ connected to a second branch of the first controlled switch bank; a second controlled switch bank having an input and a capacitively coupled output, wherein the capacitively coupled output of the second controlled switch bank comprises a third capacitor C₃ connected to a first branch of the second controlled switch bank and a fourth capacitor C₄ connected to a second branch of the second controlled switch bank; a transconductance amplifier having a first polarized input, a second, oppositely polarized input, and a capacitively coupled transconductance amplifier output; a first charge pump having inputs accepting the reference frequency signal, f_(ref), and its complement f_(ref) , respectively, output of the charge pump being connected to the input of the first controlled switch bank, individual switches of the controlled switch bank being controlled by the outputs of the reference fixed frequency divider, the output of the first controlled switch bank being connected to the first polarized input of the transconductance amplifier, wherein the capacitively coupled output of the first controlled switch bank having an output voltage of ${V_{x} = \frac{I_{1}T_{ref}}{2C_{1}}},$ where C₁=C₂, I₁ is the current output of the first charge pump and T_(ref) is the period of the reference frequency signal f_(ref), a second charge pump having inputs accepting the initial frequency signal, f_(o) and its complement f_(o) , respectively, output of the second charge pump being connected to the input of the second controlled switch bank, individual switches of the second controlled switch bank being controlled by the outputs of the output fixed frequency divider, the output of the second controlled switch bank being connected to the second polarized input of the transconductance amplifier, wherein the capacitively coupled output of the second controlled switch bank has an output voltage of ${V_{y} = \frac{I_{2}T_{0}}{2C_{3}}},$ where C₃=C₄, I₂ is the current output of the second charge pump and T₀ is the period of the initial frequency signal f_(o); a voltage controlled oscillator having a frequency control input connected to the transconductance amplifier output, and a pair of outputs, the outputs being the initial frequency f_(o), and its complement f_(o) , respectively, the output pair being fed back to input of the second charge pump, the divisor d being equal to 2, thereby making the frequency dividers fixed frequency divide by two circuits, wherein the capacitively coupled transconductance amplifier output has an output current of ${I_{z} = {g_{m}\left( {\frac{I_{2}T_{0}}{2C_{3}} - \frac{I_{1}T_{ref}}{2C_{1}}} \right)}},$ such that I_(z) charges or discharges a fifth capacitor C₅ to adjust its voltage to the proper value, the controlled oscillator output having a frequency of ${\frac{I_{2}C_{1}}{I_{1}C_{3}} \times f_{ref}},$ wherein g_(m) is a transconductance value of the transconductance amplifier, and the fifth capacitor C₅ has a capacitive value of the capacitively coupled transconductance amplifier output.
 2. The frequency synthesizer according to claim 1, wherein the charge pumps charge the capacitors for a complete half-cycle of the input signal.
 3. The frequency synthesizer circuit according to claim 1, wherein the voltages V_(x) and V_(y) are proportional to the periods of the frequency signals f_(ref) and the f_(o), respectively.
 4. The frequency synthesizer circuit according to claim 1, wherein the output frequency f_(o) can be adjusted precisely via capacitive ratios C₁ and C₃ to have fractional and integer multiple of the reference frequency f_(ref).
 5. The frequency synthesizer according to claim 1, wherein circuitry of the frequency synthesizer is integrated in CMOS technology, thereby featuring low voltage supply and power consumption. 